Chủ nghĩa hình thức tổng quát về hình thức điều khiển động cơ được kết nối nhiều pha dựa trên nhiều pha

Untitled SCIENCE & TECHNOLOGY DEVELOPMENT, Vol 18, No K6 2015 Trang 18 Generalized Vectorial Formalism – based multiphase series connected motors control  Eric Semail  Ngac Ky Nguyen  Xavier Kestel[.]

SCIENCE & TECHNOLOGY DEVELOPMENT, Vol.18, No.K6 - 2015 Generalized Vectorial Formalism – based multiphase series-connected motors control  Eric Semail  Ngac Ky Nguyen  Xavier Kestelyn  Tiago Dos Santos Moraes L2EP Laboratory, Arts et Métiers ParisTech, France (Manuscript Received on July 15, 2015, Manuscript Revised August 30, 2015) ABSTRACT Multiphase drives are more and more used in specific applications leading to a necessity of control strategy development This paper presents the Generalized Vectorial Formalism (GVF) theory to control multiphase series-connected permanent magnet synchronous motors (PMSM) fed by one voltage source inverter (VSI) Based on a decomposition of multiphase machine, a proposed control strategy has been achieved Some experimental results are given to illustrate this control method Keywords: Multiphase drives, Generalized Vectorial Formalism, Multiphase seriesconnected machines INTRODUCTION Higher reliability of classical 3-phase drives can be achieved by oversizing the convertermachine set but this solution increases the cost of the whole system Even if this oversizing is chosen, in case of an open circuit fault appears in one or two phases of the drive, the system cannot ensure a functioning even at reduced power Using multiphase drives instead of threephase drives, makes possible to increase the power density, fault-tolerance capability and to reduce torque pulsations at low frequencies [1, 2] In fault mode, this kind of drives is able to work at a reduced power with satisfactory performances This aspect is very important in systems which are designed for specific applications, such as offshore energy harvesting or electrical vehicles Trang 18 The multiphase theory has been developed since 10 years ago [3]-[6] in objective to understand deeply and allow using simple regulators for current and speed Based on this theory, a multiphase machine can be decomposited to some equivalent fictitious ones Classically, a three-phase machine in the Park reference frame is the simplest case where we have a d-q diphase machine and a homopolar one If the machine is star connected, the latter one is not considered Indeed, the Park (or Concordia) transformation is a linear mathematical application where machines will be modelled into the eigen space and represented by the eigen vectors of the matrix inductance In a general case where a multiphase machine is considered, the generalized Concordia (or Park) transformation is TẠP CHÍ PHÁT TRIỂN KH&CN, TẬP 18, SỐ K6- 2015 needed After the transformation, the multiphase machine is modeled by some diphase machines and some homopolar machines according to the shape of the back-electromotive force (backEMF) In a general way, to control a diphase machine, two independent currents are required That is why a 3-phase Voltage Source Inverter (VSI) is needed to supply a 3-phase machine and a n-phase VSI is required to supply a n-phase machine In the case where multiphase machines are series-connected, the model of each machine is not changed but the control is more complex since phase currents across all machines An independent functionning (speed and torque) of each machine requires a decoupled strategy of control and imposes some contraints to machine design in term of the back-EMF This paper presents firstly the theory of mutliphase machine based on the Generalized Vectorial Formalism A two series-connected 5phase machines supplied by one VSI structure is presented thereafter Some experimental results will be given to confirm the feasibility of the proposed structure GENERALIZED FORMALISM VECTORIAL In order to show that a polyphase machine is equivalent to a set of 1-phase and 2-phase machines, we have to bring out vectorial properties of the stator self inductance matrix The analysis of its properties enables the generalization of the transformation concept Of course, the matrices which generalize Park’s and Concordia’s transformations for a n-phase machine have already been defined and used in particular cases Our formalism defines a larger class of systems for which these transformations can be used This is possible because, in the vectorial approach, transformations are only the expression of vectorial properties linked to the stator inductance matrix At first, an Euclidian vector n-space is associated with an n-phase machine Then we consider that the stator inductance matrix is the characterization, in a natural base, of a linear application also called an endomorphism In the next paragraphs, we give some of its properties a n-phase machine and particularly a 5phase machine 2.1 Endomorphism and stator inductance matrix  L n s Let us consider the stator inductance matrix  of a multiphase machine We consider it as the matrix of an endomorphism s in an orthonormal base n classified as “natural” This endomorphism s has properties independent of the choice of the studying base: eigenvalues, eigenvectors and eigenspace To get them we have only to examine  L ns  As mutual inductance between two windings j and k are identical (Mjk=Mkj) then the matrix is symmetrical This symmetry implies the existence of a base of eigenvectors Moreover the eigenspaces of s are orthogonal each other and the dimension of an eigenspace Es is equal to the multiplicity order of the associated eigenvalue  For example, if the order of multiplicity is one (respectively two), the eigenspace is a vectorial line (respectively vectorial plan) To obtain an orthonormal base of eigenvectors we have only to choose in each eigenspace an orthonormal base The classic transformation matrixes of Park or Concordia are nothing else than tables that allow us to find the coordinates of these eigenvectors If the order of multiplicity of all eigenvalues is one, then there is only one orthonormal base of eigenvectors Consequently, only one transformation that keeps the power invariant can then be elaborated On the other hand, if the order of multiplicity is not one for one eigenvalue, then there is an infinity of orthonormal bases of eigenvectors Trang 19 SCIENCE & TECHNOLOGY DEVELOPMENT, Vol.18, No.K6 - 2015 Consequently an infinity of transformations keeping invariant the power can be defined This property explains the great number of transformations that have been proposed in the past 2.2 Applying to a n-phase machine In an orthogonal base n composed of the vectors  x1n , x 2n ,  , x nn  it can be defined the voltage, current and stator flux linkage vectors as follows:     v  v1x1n v2x2n vnxnn     i  i1x1n i2x2n inxnn (1) (2)      1x1n 2x2n n xnn (3) These vectors are linked by:     d  d  ss d  sf   Ri   v  Ri  dt dt dt where  ss  depends on i (4)  and sf is due to magnets on the rotor s represented by the inductance matrix  L  L11 L  Lns    21     Ln n  L s  M 12 L22  Ln n s  In is expressed as: M 13 M 23  Ln     M 1n  M n     Lnn  (5) As mentionned above, the symetrical inductance matrix leads to a base of eigenvectors whose corresponding eigenvalues are given by  det Lns    In   In this new base defined by Trang 20 d   , x 2d ,  , x nd  , endomorphism the matrix of s is given by:  1 0  Lds      0    0 2  0  0  n  (6) Each eigenvalue is associated to an eigenspace whose the dimension depends on the multiplicity of the eigenvalue For example, if there are two solutions equal to 1 , then the 1 is belong to a 2-dimensional eigenspace It can be noticed that all subspaces (the eigenspaces) are orthogonal and it can be defined as a set of fictitious magnetically independent systems For each subspace, the relationship between the voltage and the current is given by:    d j  di j   v j  Ri j   Ri j   j  ej dt dt  ej (7) is the back-electromotive force Based on equation (7), we can consider that in the new base, a multiphase can be decomposed into several fictitious machines where each machine is characterized by a resistor R, an inductance where Lkk is the self-inductance of the phase k and Ljk is the mutual inductance between the phases j and k   x where The relationship between the current vector and the flux vector is given by the endormorphism the natural frame, d  j and a vector of the back-EMF  ej According to the dimension of the eigenspace j is where the eigenvalue belong to, the fictitious machine can be monophase or diphase Let us take an example in the case of a 3-phase machine The new base is defined by the Concordia transformation where it exists a double root and a single root of eigenvalues by solving the determination det  Ls    I3   The   double root corresponds to the d-q machine and the single root is linked to the homopolar one TẠP CHÍ PHÁT TRIỂN KH&CN, TẬP 18, SỐ K6- 2015 2.3 Applying to a 5-phase machine Fig A 5-phase drive having star connection For a 5-phase PMSM, after a generalized Concordia transformation (given in equation (8)) which brings electrical variables of machine to the eigenspace, we obtain thus: one single eigenvalue, two double eigenvalues It means there are one 1dimensional fictitious machine and two 2dimensional ones They are called respectively homopolar machine, main machine and secondary machine It is not always the case where these machines exist Their presence depend on the shape of the back-EMF Indeed, the homopolar machine is created by harmonics 5*k The main machine is issue from harmonics 1, 9, 11,…, 5*k ± and the secondary is formed by harmonics 3, 7, 13,…, 5*k ± by considering only odd harmonics [3] Thus the Main Machine (MM) (resp the Secondary Machine (SM)) produces Tm (resp Ts) torque mainly thanks to the first harmonic (resp third harmonic) of the back-EMF Relationships between actual phase variables (denoted with subscripts a, b, c, d and e) and values of fictitious machines are then defined by:  C5         2        2 2 1 2 cos 4 cos 6 cos 8 cos 2 sin 4 sin 6 sin 8 sin 4 cos 8 cos 12 cos 16 cos 4 sin 8 sin 12 sin 16 sin                (8) 0 i    m  T imach  im   C5     is   is     ia  i   b  ic    id   ie  (9)   v    m  T vmach   vm   C5     vs   vs     vaN  v   bN   vcN    vdN   veN  (10) Currents and voltages obtained using this transformation can be decomposed into two subsystems associated with the main and secondary machines:  vm  vm vm  t  ;   t  im  im im   vs  vs vs  t    t  is  is is  (11) As the machine is supplied by a VSI, vmach  vvsi and consequently:     vm vmvsi ; vs vsvsi (12) Equations (13) - (16) give the mathematical model of the two fictitious machines in the new reference frame:   d   vm  Rm im  Lm im  em (13) dt   d   vs  Rs is  Ls is  es (14) dt     Ttot TmTs (15) where :     em im Tm and es is Ts (16) Equation (15) means that the total torque of the 5-phase machine is the sum of the torque created by the two fictitious machine We can consider that there is a fictitious mechanical coupling between them Trang 21 SCIENCE & TECHNOLOGY DEVELOPMENT, Vol.18, No.K6 - 2015 Controlling a 5-phase machine leads to finally control two equivalent fictitious diphase ones after the Concordia transformation Each ficitious machine is linked to some harmonics of the back-EMF as discussed previously in section 2.3 There are many works in the literature presenting the control of 5-phase machines under healthy and fault modes [6]-[12] In both operating modes, physical limits related to voltages and currents of the drive have been also studied [13]-[16] This paper focuses to control two 5-phase machine having a series connection and they are fed by two isolated DC-buses TWO SERIES-CONNECTED PHASE PMSM 5- The studied structure is shown in Fig The objective is to control independently these two machines Normally, to this, only one VSI is required but a higher functional reliability can be achieved by adding another VSI [19], specially in short-circuit inverter switch fault Controlling independently two 5-phase machines leads to a necessity of independently currents as degree of freedoms (DOF) In the present structure, there are only currents can be freely controlled That is why a specific connection between two machines is needed [20] 3.1 Modelling The special connection between the two machines can be expressed by:  i2   i2 a i2 b i2 c   L5  i1 a    L5  i1 i1b 1 0  with:  L5       0  i2 e  T i2 d i1 c i1 e  T i1 d 0 0 0 0 0 0  0  0  1  (17) (18)  The vectors i and i represent the current vectors of the 1st machine M1 and the second one M2 respectively Using equations (9), (17) and the property [C5 ]1  [C5 ]T , a relation between the current vectors of the fictitious machines is given as follows:   i    m  T imach   im   C5     is   is      i2 a   i1a  i  i   2b   1b  T  i2 c   C5   L5   i1c      i2 d  i1d   i2 e   i1e    i   m   T T  C5   L5 C5  im   C5   L5 C5  imach 1    is   is     (19) Fig Structure of two 5-phase open-end winding machines under study Trang 22 TẠP CHÍ PHÁT TRIỂN KH&CN, TẬP 18, SỐ K6- 2015 where: C5  T 1 0   L5  C5     0  0 0  0 1  0 0 1 0  0 0 Equations (19) and (20) lead to:  T T  i  i  s1  s is    im im     T T im1  im im    is is   or:    is1  im   * im1  is (20) (21) (22) Expression (22) lead to two significant things:  Thanks to the swapping connection between two machines M1 and M2, the currents of the main machine MM1 (second SM1 respectively) of the M1 are linked to the ones of the secondary SM2 (main MM2 respectively) machine of the M2 This allows to control independently two machines M1 and M2 with only free currents  In point of view of electromagnetic torque,  im1 will create a torque not only for the main machine of M1 but also for the second machine of M2 In the same manner,  is1 will contribute to the torque created in the two fictitious machines SM1 and MM2 This leads to a more complex strategy of control to decouple the previous mentioned interaction in order to obtain an independence of the two machines M1 and M2 This second conclusion is obvious to take into account for multiphase drives As mentionned above, a multiphase machine can bedecomposed into some fictitious ones representing by corresponding harmonics of the back-EMF The main machine is almost linked to the 1st (fundamental) harmonic while the second machine is affected to the 3rd harmonic Generally, the 3rd harmonic can contribute to the machine torque but when the machine is operated at high speed (constraint of voltage has to be applied), the current calculation becomes more complex, especially as in degraded mode where some degrees of freedom are lost That is why until now, there are no analytical solutions for a multiphase machine operating under limit of voltages and currents For some specific applications as electric vehicle where the drive is almost operated at high speed thanks to the flux weakening operation, a multiphase having sinusoidal back-EMF is preferred In this study, two 5-phase PMSM are considered sinusoidal As a consequence, the   back-EMF e s and e s does not exist leading to a  very simple control strategy The vector current im1 controls the torque (and/or the speed) of the machine M1 and the vector current  is1 is dedicated to the torque (and/or the speed) of the machine M2 Let’s talk about the voltages limit that two machines can be fed r v å r r r = vVSI - vVSI + vN1 N2 (23) with: r r r v = vM + vM å (24) is the sum of the phase voltages of the two machines M1 and M2 and  T vVSI  v1a N1 v1b N1 v1c  N1 v1d  N1 v1e  N1  (25)  T vVSI   v2aN2 v2'bN2 v2' cN2 v2' d N2 v2'eN2  (26)  T vN1N2  vN1N2 vN1N2 vN1N2 vN1N2 vN1N2  (27) Trang 23 SCIENCE & TECHNOLOGY DEVELOPMENT, Vol.18, No.K6 - 2015 Fig Speed control scheme are the voltages of the two VSI and the voltage between the two negative points of two DC buses, respectively M2 A simplified strategy has been implemented Voltages delivered by two VSI can be obtained by some techniques A Space Vector Modulation has been proposed in [21] to exploit better the two DC-buses In [22], some simple modulation strategies have been presented for varying the machine voltages according to the rotor speed without flux weanking operation In this paper, a bipolar modulation is chosen to maximize the voltage of machines 3.2 Control scheme It’s interesting to discuss about the voltage sharing between the two machines Indeed, by observing the equation (24), voltages of M1 and M2 can be shared in the optimal way while respecting the voltage limit fed by two VSI based on the bipolar modulation technique As the M1 and M2 are independently controlled, an optimal strategy could be employed according to technical specifications of the applications in term of torques and speeds of the two machines M1 and Trang 24 r r in this work by using vM = vM = r v å The control scheme is reported in Fig The two machines M1 and M2 are required to rorate as Ω1ref and Ω2ref PI controllers are used for speeds and currents tracking It can be noticed that only the phase currents of M1 are measured since they are the same ones acrossing the M2 by the  L5  transformation EXPERIMENTAL RESULTS In order to validate the proposed control strategy, some experimental results have been carried out Fig shows the platform for experimental verification Tab I gives some details of the drive parameters A 5-phase VSI is communicated to a dSPACE 1005 board through an I/O interface A DCprogrammable source is used to feed the drive during motor mode and recover energy during braking TẠP CHÍ PHÁT TRIỂN KH&CN, TẬP 18, SỐ K6- 2015 Fig Experimental test-bed Table Drive parameters Parameters 5-phase M1 5-phase M2 Phase resistance Rs = 2.24 [Ω] Rs = 9.1 [mΩ] Phase inductance Ls = 2.7 [mH] Ls = 0.09 [mH] Mutual induc M1 = 0.25 [mH] M1 = 0.02 [mH] Mutual induc M1 = -0.75 [mH] M2 = -0.01[mH] Pole pair number p=2 p=7 back-EMF constant En 0.51 En 0.1358 Max RMS current 15 [A] 147 [A] Maximum speed 1500 [rpm] 16000 [rpm] Maximum torque 20 [N.m] 50 [N.m] Maximum power 3.1 [kW] 15 [kW] For experimentation tests, the two machines M1 and M2 are operated under speed control Fig Experimental results in three studied cases: a) Ω2ref = 0; b) Ω2ref = 40 rad/s and Ω1ref is varying; c) Both machine’s speeds are varying Fig gives the experimental verification Three study cases have been considered The 1st one consists to keep the machine M2 at stand-still and the M1 is trained following a speed profile The second test has been realized by keeping the rotor speed of M2 at 40 rad/s and the M1 is tuned to track a speed profile For the last case, both machines M1 and M2 are operated at two different profiles of speed Based on the results given in Fig 5, we can conclude that the proposed control strategy has been verified It should be highlighted that there was no strategy for voltage sharing between M1 and M2 The speed profiles were chosen in the way that DC-buses are able to delivery enough voltages for two machines M1 and M2 Trang 25 SCIENCE & TECHNOLOGY DEVELOPMENT, Vol.18, No.K6 - 2015 CONCLUSION In this paper, a generalized vectorial formalism has been presented and applied for multiphase drives Based on this approach, two 5phase PMSM having series connection (through windings) can be independently controlled However, one assumption that all machines are sinusoidal has been made to simplify to control strategy This specific structure is suitable for applications where we have the constraint for compacity and weight of the whole systems Điều khiển động điện nhiều pha mắc nối tiếp dựa lý thuyết “Generalized Vectorial Formalism”  Eric Semail  Ngac Ky Nguyen  Xavier Kestelyn  Tiago Dos Santos Moraes L2EP Laboratory, Arts et Métiers ParisTech, France TÓM TẮT Bộ truyền động nhiều pha (hơn 3) dần áp dụng nhiều ứng dụng đặc biệt dẫn đến cần thiết việc phát triển giải thuật điều khiển truyền động Bài báo trình bày lý thuyết “Generalized Vectorial Formalism” để điều khiển hai động điện đồng nhiều pha mắc nối tiếp Hai động đồng cung cấp biến tần số nhánh biến tần với số pha động Theo lý thuyết “Generalized Vectorial Formalism”, máy điện nhiều pha tương ứng, mơ hình tốn học, với vài máy điện ảo (hai pha pha) Số lượng máy điện ảo phụ thuộc số pha cách đấu dây pha máy điện nhiều pha Dựa lý thuyết này, giải thuật đề để điều khiển cách hoàn toàn độc lập (vận tốc moment xoắn) hai động đồng nhiều pha mắc nối tiếp với biến tần Kết thực nghiệm với hai máy điện pha cho thấy đắn giải pháp điều khiển Từ khóa: Bộ truyền động nhiều pha, Generalized Vectorial Formalism, Máy điện nhiều pha mắc nối tiếp Trang 26 TẠP CHÍ PHÁT TRIỂN KH&CN, TẬP 18, SỐ K6- 2015 REFERENCES [1] H Jin, K Min, Y Jia-qiang, J Hai-bo, and L Dong, "Multiphase machine theory and its applications," in Electrical Machines and Systems, 2008 ICEMS 2008 International Conference on, 2008, pp 1-7 [2] E Levi, "Multiphase Electric Machines for Variable-Speed Applications," Industrial Electronics, IEEE Transactions on, vol 55, no 5, pp 1893-1909, 2008 [3] E Semail, A Bouscayrol, and J P Hautier, "Vectorial formalism for analysis and design of polyphase synchronous machines," European Physical Journal-Applied Physics, vol 22, no 3, pp 207-220, Jun 2003.² [4] X Kestelyn, E Semail, and J Hautier, "Vectorial multi-machine modeling for a fivephase machine," International Congress on Electrical Machines (ICEM’02), 2002 [5] L Parsa and H A Toliyat, "Five-phase permanent-magnet motor drives," Industry Applications, IEEE 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"Different virtual stator winding configurations of open-end winding fivephase PM machines for wide speed range without flux weakening operation," in Power Electronics and Applications (EPE), 2013 15th European Conference on, 2013, pp 1-8  ... để điều khiển hai động điện đồng nhiều pha mắc nối tiếp Hai động đồng cung cấp biến tần số nhánh biến tần với số pha động Theo lý thuyết “Generalized Vectorial Formalism”, máy điện nhiều pha. .. (vận tốc moment xoắn) hai động đồng nhiều pha mắc nối tiếp với biến tần Kết thực nghiệm với hai máy điện pha cho thấy đắn giải pháp điều khiển Từ khóa: Bộ truyền động nhiều pha, Generalized Vectorial... tương ứng, mơ hình tốn học, với vài máy điện ảo (hai pha pha) Số lượng máy điện ảo phụ thuộc số pha cách đấu dây pha máy điện nhiều pha Dựa lý thuyết này, giải thuật đề để điều khiển cách hoàn