Advanced Microwave Circuits and Systems pptx

I Advanced Microwave Circuits and Systems Advanced Microwave Circuits and Systems Edited by Vitaliy Zhurbenko In-Tech intechweb.org Published by In-Teh In-Teh Olajnica 19/2, 32000 Vukovar, Croatia Abstracting and non-prot use of the material is permitted with credit to the source. Statements and opinions expressed in the chapters are these of the individual contributors and not necessarily those of the editors or publisher. No responsibility is accepted for the accuracy of information contained in the published articles. Publisher assumes no responsibility liability for any damage or injury to persons or property arising out of the use of any materials, instructions, methods or ideas contained inside. After this work has been published by the In-Teh, authors have the right to republish it, in whole or part, in any publication of which they are an author or editor, and the make other personal use of the work. © 2010 In-teh www.intechweb.org Additional copies can be obtained from: publication@intechweb.org First published April 2010 Printed in India Technical Editor: Sonja Mujacic Cover designed by Dino Smrekar Advanced Microwave Circuits and Systems, Edited by Vitaliy Zhurbenko p. cm. ISBN 978-953-307-087-2 V Preface This book is based on recent research work conducted by the authors dealing with the design and development of active and passive microwave components, integrated circuits and systems. It is divided into seven parts. In the rst part comprising the rst two chapters, alternative concepts and equations for multiport network analysis and characterization are provided. A thru-only de-embedding technique for accurate on-wafer characterization is introduced. The second part of the book corresponds to the analysis and design of ultra-wideband low- noise ampliers (LNA). The LNA is the most critical component in a receiving system. Its performance determines the overall system sensitivity because it is the rst block to amplify the received signal from the antenna. Hence, for the achievement of high receiver performance, the LNA is required to have a low noise gure with good input matching as well as sufcient gain in a wide frequency range of operation, which is very difcult to achieve. Most circuits demonstrated are not stable across the frequency band, which makes these ampliers prone to self-oscillations and therefore limit their applicability. The trade-off between noise gure, gain, linearity, bandwidth, and power consumption, which generally accompanies the LNA design process, is discussed in this part. The requirement from an amplier design differs for different applications. A power amplier is a type of amplier which drives the antenna of a transmitter. Unlike LNA, a power amplier is usually optimized to have high output power, high efciency, optimum heat dissipation and high gain. The third part of this book presents power amplier designs through a series of design examples. Designs undertaken include a switching mode power amplier, Doherty power amplier, and exible power amplier architectures. In addition, distortion analysis and power combining techniques are considered. Another key element in most microwave systems is a signal generator. It forms the heart of all kinds of communication and radar systems. The fourth part of this book is dedicated to signal generators such as voltage-controlled oscillators and electron devices for millimeter wave and submillimeter wave applications. This part also covers studies of integrated buffer circuits. Passive components are indispensable elements of any electronic system. The increasing demands to miniaturization and cost effectiveness push currently available technologies to the limits. Some considerations to meet the growing requirements are provided in the fth part of this book. The following part deals with circuits based on LTCC and MEMS technologies. VI The book concludes with chapters considering application of microwaves in measurement and sensing systems. This includes topics related to six-port reectometers, remote network analysis, inverse scattering for microwave imaging systems, spectroscopy for medical applications and interaction with transponders in medical sensors. Editor Vitaliy Zhurbenko VII Contents Preface V 1. Mixed-modeS-parametersandConversionTechniques 001 AllanHuynh,MagnusKarlssonandShaofangGong 2. Athru-onlyde-embeddingmethodforon-wafer characterizationofmultiportnetworks 013 ShuheiAmakawa,NoboruIshiharaandKazuyaMasu 3. CurrentreusetopologyinUWBCMOSLNA 033 TARISThierry 4. Multi-BlockCMOSLNADesignforUWBWLANTransform-Domain ReceiverLossofOrthogonality 059 MohamedZebdi,DanielMassicotteandChristianJesusB.Fayomi 5. FlexiblePowerAmplierArchitecturesforSpectrum EfcientWirelessApplications 073 AlessandroCidronali,IacopoMagriniandGianfrancoManes 6. TheDohertyPowerAmplier 107 PaoloColantonio,FrancoGiannini,RoccoGiofrèandLucaPiazzon 7. DistortioninRFPowerAmpliersandAdaptiveDigitalBase-BandPredistortion 133 MazenAbiHussein,YideWangandBrunoFeuvrie 8. Spatialpowercombiningtechniquesforsemiconductorpowerampliers 159 ZenonR.Szczepaniak 9. FieldPlateDevicesforRFPowerApplications 177 AlessandroChini 10. ImplementationofLowPhaseNoiseWide-BandVCOwith DigitalSwitchingCapacitors 199 Meng-TingHsu,Chien-TaChiuandShiao-HuiChen 11. IntercavityStimulatedScatteringinPlanarFEMasaBase forTwo-StageGenerationofSubmillimeterRadiation 213 AndreyArzhannikov VIII 12. Complementaryhigh-speedSiGeandCMOSbuffers 227 EsaTiiliharju 13. IntegratedPassivesforHigh-FrequencyApplications 249 XiaoyuMiandSatoshiUeda 14. ModelingofSpiralInductors 291 KenichiOkadaandKazuyaMasu 15. Mixed-DomainFastSimulationofRFandMicrowaveMEMS-based ComplexNetworkswithinStandardICDevelopmentFrameworks 313 JacopoIannacci 16. UltraWidebandMicrowaveMulti-PortReectometerinMicrostrip-SlotTechnology: Operation,DesignandApplications 339 MarekE.BialkowskiandNorhudahSeman 17. BroadbandComplexPermittivityDeterminationforBiomedicalApplications 365 RadimZajíˇcekandJanVrba 18. MicrowaveDielectricBehaviorofAyurvedicMedicines 387 S.R.Chaudhari,R.D.ChaudhariandJ.B.Shinde 19. AnalysisofPowerAbsorptionbyHumanTissueinDeeplyImplantable MedicalSensorTransponders 407 AndreasHennig,GerdvomBögel 20. UHFPowerTransmissionforPassiveSensorTransponders 421 TobiasFeldengut,StephanKolnsbergandRainerKokozinski 21. RemoteCharacterizationofMicrowaveNetworks-PrinciplesandApplications 437 SomnathMukherjee 22. SolvingInverseScatteringProblemsUsingTruncatedCosine FourierSeriesExpansionMethod 455 AbbasSemnaniandManoochehrKamyab 23. ElectromagneticSolutionsfortheAgriculturalProblems 471 HadiAliakbarian,AminEnayati,MaryamAshayerSoltani, HosseinAmeriMahabadiandMahmoudMoghavvemi Mixed-modeS-parametersandConversionTechniques 1 Mixed-modeS-parametersandConversionTechniques AllanHuynh,MagnusKarlssonandShaofangGong x Mixed-mode S-parameters and Conversion Techniques Allan Huynh, Magnus Karlsson and Shaofang Gong Linköping University Sweden 1. Introduction Differential signaling in analog circuits is an old technique that has been utilized for more than 50 years. During the last decades, it has also been becoming popular in digital circuit design, when low voltage differential signaling (LVDS) became common in high-speed digital systems. Today LVDS is widely used in advanced electronics such as laptop computers, test and measurement instrument, medical equipment and automotive. The reason is that with increased clock frequencies and short edge rise/fall times, crosstalk and electromagnetic interferences (EMI) appear to be critical problems in high-speed digital systems. Differential signaling is aimed to reduce EMI and noise issues in order to improve the signal quality. However, in traditional microwave theory, electric current and voltage are treated as single-ended and the S-parameters are used to describe single-ended signaling. This makes advanced microwave and RF circuit design and analysis difficult, when differential signaling is utilized in modern communication circuits and systems. This chapter introduces the technique to deal with differential signaling in microwave and millimeter wave circuits. 2. Differential Signal Differential signaling is a signal transmission method where the transmitting signal is sent in pairs with the same amplitude but with mutual opposite phases. The main advantage with the differential signaling is that any introduced noise equally affects both the differential transmission lines if the two lines are tightly coupled together. Since only the difference between the lines is considered, the introduced common-mode noise can be rejected at the receiver device. However, due to manufacturing imperfections, signal unbalance will occur resulting in that the energy will convert from differential-mode to common-mode and vice versa, which is known as cross-mode conversion. To damp the common-mode currents, a common-mode choke can be used (without any noticeable effect on the differential currents) to prevent radiated emissions from the differential lines. To produce the electrical field strength from microamperes of common-mode current, milliamperes of differential current are needed (Clayton, 2006). Moreover, the generated electric and magnetic fields from a differential line pair are more localized compared to 1 AdvancedMicrowaveCircuitsandSystems2 those from single-ended lines. Owing to the ability of noise rejection, the signal swing can be decreased compared to a single-ended design and thereby the power can be saved. When the signal on one line is independent of the signal on the adjacent line, i.e., an uncoupled differential pair, the structure does not utilize the full potential of a differential design. To fully utilize the differential design, it is beneficial to start by minimizing the spacing between two lines to create the coupling as strong as possible. Thereafter, the conductors width is adjusted to obtain the desired differential impedance. By doing this, the coupling between the differential line pair is maximized to give a better common-mode rejection. S-parameters are very commonly used when designing and verifying linear RF and microwave designs for impedance matching to optimize gain and minimize noise. Although, traditional S-parameter representation is a very powerful tool in circuit analysis and measurement, it is limited to single-ended RF and microwave designs. In 1995, Bockelman and Einsenstadt introduced the mixed-mode S-parameters to extend the theory to include differential circuits. However, owing to the coupling effects between the coupled differential transmission lines, the odd- and even-mode impedances are not equal to the unique characteristic impedance. This leads to the fact that a modified mixed-mode S- parameters representation is needed. In this chapter, by starting with the familiar concepts of coupling, crosstalk and terminations, mixed-mode S-parameters will be introduced. Furthermore, conversion techniques between different modes of S-parameters will be described. 2.1 Coupling and Crosstalk Like in single-ended signaling, differential transmission lines need to be correctly terminated, otherwise reflections arise and distortions are introduced into the system. In a system where parallel transmission lines exist, either in differential signaling or in parallel single-ended lines, line-to-line coupling arises and it will cause characteristic impedance variations. The coupling between the parallel single-ended lines is also known as crosstalk and it is related to the mutual inductance (L m ) and capacitance (C m ) existing between the lines. The induced crosstalk or noise can be described with a simple approximation as following ܸ ௡௢௜௦௘ ൌ ୫ ୢ୍ ౚ౨౟౬౛౨ ୢ୲ (1) ܫ ௡௢௜௦௘ ൌܥ ௠ ௗ௏ ೏ೝ೔ೡ೐ೝ ௗ௧ (2) where V noise and I noise are the induced voltage and current noises on the adjacent line and V driver and I driver are the driving voltage and current on the active line. Since both the voltage and current noises are induced by the rate of current and voltage changes, extra care is needed for high-speed applications. The coupling between the parallel lines depends firstly on the spacing between the lines and secondly on the signal pattern sent on the parallel lines. Two signal modes are defined, i.e., odd- and even-modes. The odd-mode is defined such that the driven signals in the two adjacent lines have the same amplitude but a 180 degree of relative phase, which can be related to differential signal. The even-mode is defined such that the driven signals in the two adjacent lines have the same amplitude and phase, which can be related to common- mode noise for a differential pair of signal. Fig. 1 shows the electric and magnetic field lines in the odd- and even-mode transmissions on the two parallel microstrips. Fig. 1a shows that the odd-mode signaling causes coupling due to the electric field between the microstrips, while in the even-mode shown in Fig 1b, there is no direct electric coupling between the lines. Fig. 1c shows that the magnetic field in the odd-mode has no coupling between the two lines while, as shown in Fig. 1d, in the even-mode the magnetic field is coupled between the two lines. a. electric field in odd-mode b. electric field in even-mode c. magnetic field in odd-mode d. magnetic field in even-mode Fig. 1. Odd- and even-mode electric and magnetic fields for two parallel microstrips. 2.2 Odd-mode The induced crosstalk or voltage noise in a pair of parallel transmission lines can be approximated with Equation 1. For the case of two parallel transmission lines the equation can be rewritten as following ܸ ଵ ൌܮ ଴ ௗூ భ ௗ௧ ൅ܮ ௠ ௗூ మ ௗ௧ (3) ܸ ଶ ൌܮ ଴ ௗூ మ ௗ௧ ൅ܮ ௠ ௗூ భ ௗ௧ (4) where L 0 is the equivalent lumped-self-inductance in the transmission line and L m is the mutual inductance arisen due to the coupling between the lines. Signal propagation in the odd-mode results in I 1 = -I 2 , since the current is always driven with equal magnitude but in opposite directions. Substituting it into Equations 3 and 4 yeilds ܸ ଵ ൌ ሺ ܮ ଴ െܮ ௠ ሻ ௗூ భ ௗ௧ (5) Current into the page Current out of the p a g e [...]... into consideration in this chapter Further studies can be done for verification of the theory 12 Advanced Microwave Circuits and Systems 5 References Bockelman D E and Eisenstadt W R., Combined Differential and Common-Mode Scattering Parameters: Theory and Simulation IEEE transactions on microwave theory and techniques, Vol 43, No 7, pp.1530-1539, July 1995 Clayton P.R Introduction to Elecctromagnetic... into Equations 35-38 and assuming that Zoo = Zoe = Z0, yields the following results 10 ��� � ��� � Advanced Microwave Circuits and Systems ����� ���� √� ����� ���� √� ������������� � ������������� � ����� ���� √� (41) ����� ���� √� (42) As shown by Equations 41 and 42 the differential incident and reflected waves can be described by the single-ended waves Inserting Equations 41 and 42 into Equation... two termination configurations, i.e., Pi- and T-terminations, which can terminate both the odd- and even-mode signals in coupled parallel transmission lines Fig 2 Variation of the odd- and even-mode impedances as a function of the spacing between two parallel microstrips V1 R3 V2 a Pi-termination R1 R2 + - Differential reciever 6 Advanced Microwave Circuits and Systems V1 R1 R3 R2 + - V2 Single-ended... agreement between the measurement data and the model up to 100 GHz The procedure of the thru-only de-embedding method ((Ito & Masu, 2008; Laney, 2003; Nan et al., 2007; Song et al., 2001; Tretiakov et al., 2004a)) is as follows The 2-port containing the DUT and the THRU a are assumed to be representable by Fig 1(a) and Fig 1(b), respectively 16 Advanced Microwave Circuits and Systems 0.55Ω 16 pH 16 pH 0.55Ω... consistent with the common mode and the differential mode in analog circuit theory (Gray et al., 2009) The differential mode gives what is interpreted as the signal in 22 Advanced Microwave Circuits and Systems (a) (b) L DUT R L R Fig 8 (a) Model of an as-measured 4-port The DUT is embedded in between the intervening structures L and R (b) Model of a THRU dummy pattern differential circuits The common mode... 12, and hence the division of S, a, and b into submatrices/subvectors: b= b1 b2 = S11 S21 S12 S22 a1 a2 = Sa (64) 26 Advanced Microwave Circuits and Systems S′, S′̃ S, T, S̃ 1′ a1 2′ n+2 4′ 3 n+3 6′ 4 7′ 5′ n+1 2 3′ b1 1 n+4 8′ a2 b2 2n-port (2n−3)′ n−1 (2n−1)′ 2n−1 n 2n (2n−2)′ (2n)′ Fig 12 Port indices for a cascadable 2n-port The ports 1 through n of S constitute one end of the bundle of n lines and. .. al., 2009) A 2n-port THRU can be regarded as nonuniform multiconductor transmission lines, 14 Advanced Microwave Circuits and Systems PAD left DUT PAD right TL Tdut TR Tmeas (a) A test pattern with pads and a DUT PAD left PAD right TL TR Z/2 Y Z/2 Y Tthru (b) Model of THRU Fig 1 DUT embedded in parasitic networks and its scattering matrix can be transformed into a block-diagonal form with 2 × 2 diagonal... accurate microwave and millimeter-wave characterization of on-chip multiport networks It also has the advantage of not requiring a large area of expensive silicon real estate 2 Introduction Demand for accurate high-frequency characterization of on-chip devices has been escalating concurrently with the accelerated development of high-speed digital signaling systems and radio-frequency (RF) circuits. .. OPEN and SHORT on-chip standards (dummy patterns) (Wartenberg, 2002) De-embedding procedures are becoming increasingly complex and tend to require several dummy patterns (Kolding, 2000b; Vandamme et al., 2001; Wei et al., 2007) The high cost associated with the large area required for dummy patterns is a drawback of advanced de-embedding methods Thru-only methods, in contrast, require only one THRU and. .. lines Signal propagation in the odd-mode results in I1 = -I2, since the current is always driven with equal magnitude but in opposite directions Substituting it into Equations 3 and 4 yeilds (5) 4 Advanced Microwave Circuits and Systems �� � ��� � �� � � �� �� (6) This shows that, due to the crosstalk, the total inductance in the transmission lines reduces with the mutual inductance (Lm) Similarly, the . I Advanced Microwave Circuits and Systems Advanced Microwave Circuits and Systems Edited by Vitaliy Zhurbenko In-Tech intechweb.org Published. single-ended signaling. This makes advanced microwave and RF circuit design and analysis difficult, when differential signaling is utilized in modern communication circuits and systems. This chapter introduces. 291 KenichiOkada and KazuyaMasu 15. Mixed-DomainFastSimulationofRF and Microwave MEMS-based ComplexNetworkswithinStandardICDevelopmentFrameworks 313 JacopoIannacci 16. UltraWideband Microwave Multi-PortReectometerinMicrostrip-SlotTechnology: Operation,Design and Applications